Variable speed constant frequency system



y 5. 1969 L. R. PEASLEE Re. 26,630

VARIABLE SPEED CONSTANT FREQUENCY SYSTEM Original Filed Aug. 7. 1961 12Sheets-Sheet 2 '1- FIG. 2

m a [I48 FIG. l2

IZV v as 234 2O0K1-252 a -1- 224! 220 47K gl 47K I 226 ---"|94 INVENTOR.LAWRENCE R.PEASLEE FIGJO BY 4v ATTORNEY July 15, 1969 R. PEASLEEVARIABLE SPEED CONSTANT FREQUENCY SYSTEM Original Filed Aug. 7, 1961 12Sheets-Sheet 5 muhmioczwkoa INVENTOR. LAWRENCE R.PEAS LEE r/MM ATTORNEYJuly 15, 1969 L. R. PEASLEE VARIABLE SPEED CONSTANT FREQUENCY SYSTEM 12Sheets-Sheet 5 Original Filed Aug. 7, 1961 E E a WA in mR E c N E R w AL mu; g

7.. 6 3383. X E J- uuzufihmz I n Hg "Zul b Owl fill. /T utmsm 3 JW MATTORNEY July 15, 1969 1.. R. PEASLEE VARIABLE SPEED CONSTANT FREQUENCYSYSTEM 12 sheets-Shu a e Urizinal Filed Aug. 7. 1961 moo 10.5 50 mutuxuQOm INVENTOR. LAWR E NCE RPEASLEE AT TO RN EY July 15, 1969 L.. R.PEASLEE VARIABLE SPEED CONSTANT FREQUENCY SYSTEM 12 Sheets-Sheet 7Original Filed Aug. '7, 1961 Sow- .2600 no 024 Fan-P30 S89E26 92 50.5 558 4 52a 6 32b H2: wziouz E: 5.58 55 532 INVENTOR. LAWRENCE R.PEASLEEATTORNEY July 15, 1969 1.. R. PEASLEE VARIABLE SPEED CONSTANT FREQUENCYSYSTEM Original Filed Aug. 7. 1961 12 Sheets-Sheet 8 b.3950 Imhmrm Nn uwm 1m U n 3 0 um 2 m P 5th.; 31E m uwst Q24 $5 383 w 9:; no N k 03 73.6

:3 35.... I I, llll I I I MMW mlm l l mol IW MUI I I I I 138m. 3 25 -nh. Ev H fl o: 3 u N 3v 6 3v m II IIIIIW 3v E... w? ON f x 2b .7 95 5'3t" m I 09 P I I I I I I I I I I I I I I I I IIL N...

933.63 n 92 .Sfiao 55 368 uni... no 396 54: .15 2:2! m9. 2250.. @0253: i

INVENTOR. LAWRENCE R. PEASLEE ATTORNEY 12 Sheets-Sheet 9 Original FiledAug. 7. 1961 FIG.I6

I FREQUENCY I CONVERSION PHASE C I I I I I I I I I I I I I I I I I I I IPHASE C PHASE B PHSE FROM OSCILLATOR TRAINING CIRCUIT PHA B FROMOSCILLATOR ILTER INVENTOR LAWRENCE R. PEAS LEE ATTORNEY FIG.I4

FIG.I7

July 15, 1969 L. R. PEASLEE VARIABLE SPEED CONSTANT FREQUENCY SYSTEM 12Sheets-Sheet 10 Original Filed Aug. 7, 1961 E E .L w s x535: T A 553E mE W R I E G35 G35 5%.. m z2mm z3 55558 M 8 5233f. 8 65:85: W A SE3 m3;wz 5150 SEE? GE; wza. L Y 44902 55 muse. 3459 $2 368 3933.5 EEK mo bo102 368 B 530.. :21 355mm 532 :9: 35%;? f 4 f N fiozwmmE 3 :3 $582ATTQRNEY July 15, 1969 R. PEASLEE 26,630

VARIABLE SPEED CONSTANT FREQUENCY SYSTEM Original Filed Aug. 7. 1961 12Sheets-Sheet 1] I l FIG. l9 a I SUPPLY I HALF wave 8 Y T o.ov l I FIRINGPOINT F|G I9b l cosme WAVE APPLIED TO 1 l SWITCHING DEVICE GATE r 1 GATETHRESHOLD l NO OFFSETO i l I a l I F|G IQ FIRING POINT I 1 i *GATETHRESHOLD OFFSET FIRING POINT INVENTOR- LAWRENCE R. PEASLEE ATTORNEYJuly 15, 1969 R. PEASLEE VARIABLE SPEED CONSTANT FREQUENCY SYSTEMOriginal Filed Aug. 7. 1961 12 Sheets-Sheet 12 moo-mun- 2050:0200

INVENTOR.

ATTORNEY LAWRENCE R. PEASLEE u u am 55655 umumiq 0 0 q 35 on NNGE UnitedStates Patent 26,630 VARIABLE SPEED CONSTANT FREQUENCY SYSTEM LawrenceR. Peaslee, Waynesboro, Va., assignor to general Electric Company, acorporation of New ork Original No. 3,152,297, dated Oct. 6, 1964, Ser.No. 129,646, Aug. 7, 1961. Application for reissue May 25, 1966, Ser.No. 559,031

Int. Cl. H02m 1/08 US. Cl. 321-69 13 Claims Matter enclosed in heavybrackets appears in the original patent but forms no part of thisreissue specification; matter printed in italics indicates the additionsmade by reissue.

This invention relates to frequency converter systems. [Moreparticularly, it relates to a system for providing an output having arange of determinate frequencies from a variable speed source] Incopending application Ser. No. 536,149 filed Mar. 21, 1966 by D. L.Plette (which is a continuation of application Ser. No. 122,278, filedJuly 6, 1961, and which is assigned to the same assignee as this presentapplication) there is disclosed a frequency conversion system forproviding a range of determinate frequencies from a variable speedsource.

Copending application Ser. No. 562,032, filed June 2, 1966 by L. R.Peaslee and S. C. Caldwell (which is a reissue application of U.S.Patent 3,148,324 and which is assigned to the same assignee as thispresent application) and the present application disclose and claimimprovements on the invention of Plette. The claims in thePeaslee-Caldwell application are directed to a frequency conversionsystem in which the modulation function is improved by sinusoidal tocosinusoidal signal conversion and also by the addition of means toinsure that gating signals are applied to the switching devices onlywhen these devices are in a conductive condition. The claims in thepresent application are directed to a frequency conversion system havingatzalog feedback to improve the output waveshape.

In many situations such as aircraft systems or other arrangementswherein an engine whose speed varies over a wide range is utilized topower an electric generator, it has been desirable to obtain a constantfrequency output having a chosen range of determinate frequencies fromthe variable speed source provided by such engine. Herctofore, the mostwidely used device for this purpose has been a hydraulic constant speeddrive which is essentially a hydraulic generator-motor system thatutilizes either a variable displacement generator or a motor incontinuously variable ratio over a requisite input speed range.

Such transmissions which are in general use today are quite complex andrequire extreme precision of moving parts together with associatedpiping and cooling systems. In addition, the lives of such systems arerelatively short and considerable maintenance thereof is required. Also,overhead costs of such systems are high and development costs for newratings and speed ranges plus the production costs thereof are quiteexpensive. The speed limitations of these systems serve to inhibit thedevelopment of lighter weight systems.

It is, accordingly, an important object of this invention to provide anall-electrical system for converting the indeterminate variable shaftspeed provided by an engine or other energy source to an electricaloutput having a chosen range of determinate frequencies.

It is a further object to provide a system in accordance with thepreceding object which is relatively light in weight and has arelatively large power handling capacity.

It is another object to provide a system in accordance with thepreceding objects wherein considerable flexibility Re. 26,630 ReissuedJuly 15, 1969 and selection of input speed range and output frequency isenabled and wherein the efficiency of the system is high.

Generally speaking and in accordance with the invention, there areprovided in combination, first means to produce a plurality of likeoutputs equally displaced in phase and having an indeterminate variablefrequency, a source of reference voltage having a given range ofdeterminable frequencies, the highest frequency of the range generallybeing less than the lowest frequency of the outputs and second means incircuit with the reference voltage source and the first means for mixingthe outputs and the reference voltage. There are also included thirdmeans in circuit with the first means to produce first signal conditionsin response to half cycles of one polarity of the outputs and secondsignal conditions in response to half cycles of the opposite polarity ofthe outputs and fourth means in circuit with the second and third meansfor producing first and second signals during such signal conditions inresponse to the application of the resultant of the mixing of theoutputs and the reference voltage. Means are further included to combinethe signals to produce an output having the frequency of the referencevoltage.

The features of this invention which are believed to be new are setforth with particularity in the appended claims. The invention itself,however, may best be understood by reference to the followingdescription when taken inconjunction with the accompanying drawingswhich show embodiments of a frequency converter according to theinvention.

In the drawings,

FIG. 1 is a block diagram of a system in accordance with the invention;

FIG. 2 is a diagram conveniently utilized for explaining the inventiveconcept of the system;

FIG. 3 is a block depiction of an arrangement for providing outputsignals in accordance with a simulated embodiment of the system;

FIGS 4a-4c are depictions of the circuit symbols utilized in FIG. 3;

FIG. 5 is a diagram of a portion of a modulator which is utilized in thesimulated embodiment;

FIG. 6 is a diagram useful in explaining the operation of the system ofFIG. 5;

FIGS. 7-12 are schematic diagrams of circuits utilized in the modulatorof FIG. 5; and

FIGS. 13-16 taken together as in FIG. 17 is a diagram of anotherembodiment of the system;

FIG. 18 is a depiction of a waveform useful in explaining the operationof the invention;

FIGS. 19a-19d comprise a timing diagram of Waveforms useful inexplaining the operation of the invention;

FIGS. 20 and 21 illustrate the feedback feature of the invention;

FIGS. 22a-22e comprise a timing diagram of Wave forms which occur in theoperation of the embodiment depicted in FIGS. 13-17; and

FIG. 23 is a logical diagram depicting the operation of the embodimentshown in FIGS. l3l7.

Referring now to FIG. 1 wherein there is shown an embodiment of a systemin accordance with the invention, a generator 10 in response to theapplication thereto of the variable speed power from shaft 12 produces athree phase output, viz, phase e e and c having a frequency inaccordance with the speed of shaft 12. The field winding 14 of generator10 is excited by an exciter 16 which may suitably be of the static type,there being fed back to a voltage regulator contained in exciter 16, thephase e e and c outputs of the generator 10 to provide thereby voltageregulation of the outputs of generator 10.

For providing three outputs from the system which are equally displacedin phase, viz., phases A, B and C, a modulator and a frequencyconversion stage are provided for producing each output. Thus, for phaseA, there are provided a modulator 18 and a frequency conversion stage20. For phase B, there are provided a modulator 22 and a frequencyconversion stage 24, and for phase C, there are provided a modulator 26and a frequency conversion stage 28. An oscillator and phase splitter 30having a three phase output of a given range of determinable frequenciesprovides a reference frequency voltage for modulators 18, 22 and 26.

In the frequency conversion stages 20, 24 and 28, there are includedpower switching devices which are rendered conductive in response toswitching signals respectively applied thereto to perform the frequencyconversions in the system. The outputs of the frequency conversionstages 20, 24 and 28 are combined in combiners 32, 34 and 36,respectively. Since the unfiltered outputs of the combiners containcomponents having undesired frequencies, the output filters 38, 40 and42 substantially remove such undesired components.

In the modulators, one of the respective phase outputs of oscillator 30is mixed with the three phase outputs of generator to provide the properswitching signals for the power switching devices in the frequencyconversion stages respectively. The exciter regulator 16 functions tocontrol the excitation in generator 10 so that the proper voltages areapplied to the frequency converters.

Oscillator stage 30 contains an oscillator, the frequency of the outputof which determines the frequency of the output of the system. The threebalanced phase outputs from oscillator stage 30 are derived by means ofa phase splitter or like device, which determines the system phasedisplacement and phase sequence. The frequency of generator 10 issuitably chosen to be about 4 to 20 times the oscillator frequency.

Analog feedbacks of the respective system phase outputs to thecorresponding modulators serve to reduce distortion of the output of thesystem and also to provide a degree of voltage regulation.

In the frequency conversion stages, a plurality of first switchingdevices is controlled by the positive half cycles of the outputs ofgenerator 10 and another such plurality of second switching devices iscontrolled by the negative half cycles of the outputs of generator 10.The restraining circuits 44, 46 and 48 serve to insure that nocommutation occurs between the respective first and second pluralitiesof switching devices in an associated fre quency conversion stage unlessthe current in the output of the associated combiner is passing throughor already has passed through the zero crossover point. The currents inthe outputs of combiners 32, 34 and 36, respectively, are sensed bycurrent transformers 50, 52 and 54, the current in transformers 50, 52and 54 being fed to restraining circuits 44, 46 and 48 respectively.

In FIG. 2, there is shown a circuit which depicts the circuitrelationships in one phase of the system of the invention. In thiscircuit, the generators 37, 39, 41 produce the three outputs 120displaced in phase with respect to each other, each output, viz,voltages e e and c having the same varying frequency. The seriesinductance l represents the total commutating inductance of the system.The normally open relay contacts R R and R, which represent thenonconductive conditions of the switching devices in a frequencyconversion stage of FIG. 1, when they assume the closed position, switchthe output of the system from one generator phase to another as effectedby gating signals applied to the switching devices (not shown)respectively associated with contacts R R and R In the operation of thecircuit of FIG. 2, the switching devices associated with contacts R Rand R respectively, are energized in accordance with the output of amodulator (FIG. 5) wherein the three balanced generator voltages e e eare mixed with a reference voltage having a determinate frequency.Preferably the frequency of the reference voltage is such that the rangeof frequencies of the generator voltages is about from four to twentytimes [as great thereof] greater. Of course, three reference voltagesare provided where there are three frequency converter stages and areequally displaced in phase with respect to each other as are thegenerator voltages, the mixing occurring in each phase in the modulatorbetween the three phase generator voltages and one of the referencevoltage phases.

The output passed through alternately closed contacts R R and R isfiltered through filter inductance 1 and capacitance C and developedacross load inductance L and resistance R to provide the output voltagee for a system phase output.

In the circuit of FIG. 2, in the relationships obtaining therein, asshown hereinbelow, classical notation rather than operational notationis utilized to more directly preserve identification between measuredquantities and the physical components of the actual system. Therelationships are:

e =e sin 21rf t; e =a e e =ae,; a=e

where f,,: generator frequency e =e sin 21rf t where f =output frequencyl sl i with no amortisseurs (generator transient inductance) withamortisseurs (generator sub-transient inductance) 1=filter inductanceL=load inductance C=filtcr capacitance ri=equivalent resistance of thecore loss in inductance 1 R=load resistance The current equations of thesystem are:

where e,=e e or e whichever is connected to the filter input at the timeconsidered.

Equation a represents the current flowing in the generator and mayconsist of: no currents, current in one phase or current in two phasesdepending upon the condition of the system at the time considered.Equation b represents the sums of the currents flowing through theinductance and resistance branches, 1 and r of FIG. 2. Equation crepresents the total current flow into the shunt branches C, R and L inFIG. 2.

When Equations a and b are solved simultaneously there results:

and when Equations b and c are solved simultaneously, there results:

In FIG. 3, there is shown a circuit for producing the three balancedgenerator voltages e c and e, and output voltages e and e as set forthin Equations d and e. In FIGS. 4a, 4b and 40, there are shown thesymbols utilized in depicting the system elements in the circuit of FIG.3.

In the circuit of FIG. 3, Equation d is represented by integrators 58,60, 62 and 66 and summers 64 and 68. The outputs of integrators 58, 60and 62 are respectively equal to the currents in phases e e and emultiplied by the factor I (FIG. 2). The output of integrator 66 is thefactor r times the current in the inductive branch of the series filterinductor 1 (FIG. 2), and the current in the resistive branch of theseries filter is the factor times the difference between e and c Thesystem output voltage is e Equation e is represented in FIG. 3 byintegrators 76 and 86 and summer 78. The potentiometers 49, 51, 53, 65,70, 72, 74, S0, 82 and 84 may be utilized in varying the system loadingwith each potentiometer being a loading element. Integrators 43 and 47,together with summers 45, 55 and 56 provide the three phase voltagesource, viz, voltages e e and 0 In FIG. 5, there is shown a portion of amodulator circuit which may be utilized with the computer circuit ofFIG. 3. The circuit of FIG. essentially has two functions. viz, thesupplying of the necessary information to fire the simulated switchingdevices therein (silicon controlled rectifiers being the type of devicesthat are simulated), according to a predetermined schedule (as modifiedby an analog feedback signal) and to provide additional logic to thesimultated silicon controlled rectifiers whereby they properly performall the functions of silicon controlled rectifiers.

In this figure, the output of one phase of a polyphase variablefrequency oscillator 90, which can be conveniently designated as voltagee is applied through a resistor 92 as one input to a DC amplifier 96.Also, applied through resistors 93 and 95 as inputs to DC. amplifier 96are the generator phase outputs e and e Resistor 93 is chosen to have avalue which is twice the value of resistors 92 and 95. Since signals eand e are 120 displaced in phase with respect to each other, the outputof amplifier 96 may be conveniently designated as e :e cos e In FIG. 18there is shown the wave shape of the signal e In this wave shape, if theamplitude of the output of the oscillator wave is taken to have a valueof one, then the amplitude of the generator voltage superimposed thereonis one-half. The positive gate threshold line in FIG. 18 also has anamplitude of onehalf and indicates the voltage level above which asilicon controlled rectifier controlled by a positive half cycle ofgenerator voltage is switched into conductivity. The line in FIG. 18designated negative gate threshold" indicates the voltage below which asilicon controlled rectifier controlled by the negative half cycles ofgenerator output is switched into conductivity.

It is to be noted that the generator signal superimposed on theoscillator signal in FIG. 18 is a cosinusoid. This is readilyappreciated that from the fact that since c and e;, are 120 displaced inphase with respect to each other and since the value of resistor 93 istwice that of resistor 95, the summing in amplifier 96 provides thecosinusoid of the e, voltage.

Prior to describing the remainder of the modulator of FIG. 5, it is tobe realized that the purpose of this modulator is to construct a firingschedule which will produce the best sine wave power output for a givenfilter or, conversely, to produce a sine wave of a given quality withthe least filtering. In this connection, it is to be noted that thefilter itself is not the only part affected. Thus, if the filter seriesinductance increases in size, the generator must also increase in sizeto supply the added voltage drop across such inductance.

It has been found that if the generator output is directly superimposedon the reference oscillator wave, in the event that there are presentdifferent power factors in the generator output, the sine waves from thegenerator superimposed upon the oscillator wave are distorted.Accordingly, it is first desired to vary the firing angle of theswitching device as a function of the instantaneous height of the firingcurve.

The latter can be accomplished by producing a cosinusoid from thegenerator voltage and utilizing it, as shown in FIGS. 19a-d. In FIG. 19athere is shown a half cycle of voltage from a generator output. In FIG.19b, there is shown a cosine wave derived from the wave of FIG. 19a withno offset. In FIG. 19c there is shown the same cosine wave with anoffset whereby the gate threshold is at the crossover point of halfcycles of the cosinusoid. In FIG. 19d, there is shown a cosinusoid wavewith an offset whereby the gate threshold is at the most negative pointof the wave. It is seen from FIGS. 19c and 19d that if a cosinusoidhaving the same frequency as the generator output is varied up and downwith an offset, the point at which the switching device is actuated canreadily be varied from 0 to Thus, if the cosinusoid is added to theoscillator wave as shown in FIG. 18, the firing angle can be made toprogress smoothly from conduction periods of 0 to full conduction andback to 0 as the curve rises and falls.

To obtain such performance, gate thresholds and magnitudes are set ashas been described in connection with FIG. 18. In FIG. 18, the amplitudeof the oscillator wave, is taken to be one, the amplitude of thecosinusoid taken to be one-half and the amplitudes of the positive andnegative gate thresholds, respectively, are plus and minus one-half.With this arrangement, there is enabled a variation of conduction anglein the switching device as a function of the instantaneous oscillatorwave magnitude.

It is also desired to shape the firing curve as a function of load andpower factor to produce the best sine wave output from the filter. It isrealized that a modulator and a frequency conversion stage (FIG. 1)together provide a power amplifier of considerable power gain as shownin FIG. 20. Parts of the converter are extremely non-linear but theoperation desired is that of a high power linear amplifier. To linearizethe power amplifier, feedback is utilized such as shown in FIG. 21. Withfeedback, the power gain is reduced. However, the obtainable power gainwith switching devices is very great. Accordingly, the power of thereference voltage may be small proportionately.

The feedback signals obtained from the output voltage (FIG. 21) may beconsidered as consisting of two parts; a first type feedback comprisingthe fundamental output frequency and its harmonics and a second typefeedback comprising the modulated ripple voltage derived from themultiple switching of the generator voltages. The system describedherein operates reasonably well with only the first type of feedback.This feedback regulates the output voltage and improves the wave shapesomewhat. However, when the second type feedback is also utilized, theoutput wave shape is greatly improved and the stability margin isimproved, this improvement of the stability margin permitting the firsttype feedback to be appreciably increased. When the second type feedbackis utilized by itself, it effects an appreciable improvement in waveshape although the voltage regulation is not as complete as may bedesired. Thus, the combination of both types of feedback give the bestoverall results.

The second type of feedback is helpful in improving wave shape becauseit is carrying intelligence to each switching device, i.e., each siliconcontrolled rectifier. The steep slope of such modulated ripple makes itseffect very definitive. The second type feedback is especially helpfulin correcting wave shape with a low power factor load.

Thus, with feedbacks as set forth, a sine wave input from the generatorand filtering, the needed shaping of the firing curve for the switchingdevice to produce a sinusoidal power output for a minimum filter size isobtained for any load condition. It is to be noted that using both typesof feedback provides the following advantages:

(1) The feedback shapes the output wave to correspond closely to theoscillator wave input, the voltage regulation function being obtainedautomatically with a response time of much less than a cycle of thepower output sine wave.

(2) Since the feedback has in effect provided a linearized amplifier,the power output waveform closely conforms to any input referenceoscillator waveform of any frequency up to a fraction of the relativelyhigh generator frequency. With this arrangement, high power squarewaves, sawtooth waves and other complex waveforms are obtainable.

Referring now back to the modulator depicted in FIG. 5, it is seen thatexpression produces the cosine of e Applied as inputs to DC. amplifier102 through resistors 98 and 100 are the signals c and -e' as derivedfrom the computer shown in FIG. 3. Produced at the output of amplifier102 is the signal e which is the negative voltage across a simulatedback to back silicon controlled rectifier pair, e being equal to e -e'.The signal e is the negative of a voltage proportional to the currentfrom the output of phase e and is the ri signal from the computer inFIG. 3.

To understand the relationship of the circuit of FIG. to the system ofFIG. 1, it is to be understood that there is shown in FIG. 5 only aportion of a modulator for mixing one of the generator outputs, forexample, the e output with a phase output of the reference voltageoscillator. The portion of the modulator shown in FIG. 5 determines thefiring schedule for a back to back pair of switching devices in circuitwith the e, phase output of the generator. By the term back to back pairof switching devices is meant a pair of switching devices where one isswitched into conductivity during the positive half of a cycle of agenerator output and the other is switched into conductivity during thenegative half of such cycle. Thus, the back to back pair of devices, oneof which is conveniently designated as R i.e., the device which isswitched into conductivity during the positive half cycle of a generatoroutput, and the other of which is designated R i.e., the device which isswitched into conductivity during the negative half cycle of the samegenerator output are suitably in circuit with a generator output such ase, to effect such switching. The devices that are simulated are siliconcontrolled rectifiers.

To provide a single phase output of a system, each modulator, therefore,would include a circuit such as shown in FIG. 5 for each back to backpair of switching devices, the number of each back to back pair ofswitching devices being determined by the number of balanced phaseoutputs respectively from the generator. Thus, for each phase of systemoutput, i.e., outputs having the frequency and phases of the outputsreference oscillator, there would be required a modulator, eachmodulator comprising a number of circuits such as that depicted in FIG.5, such number being equal to the number of back to back pairs ofswitching devices in the frequency converter for each stage, i.e., thenumber of different phase outputs of the generator.

The e signal is supplied to a neutral zone circuit comprising seriesconnected unidirectional potential sources 101 and 103 in shunt with theseries connected diodes 105 and 107, the -e signal being applied to thejunction 109 of the cathode of diode 107 and the anode of diode 105.There is taken from the junction 111 of sources 101 and 103, the signale The signal e which is the e, output of the computer of FIG. 3 isapplied to an input sensing amplifier 108. Sensing amplifier 108 issuitably an amplifier which normally provides approximately zero voltsoutput when the input thereto is less than zero and a minus voltage, sayabout 6 volts when the input is equal to or exceeds zero volt.Consequently, amplifier 108 inverts the e voltage and the output thereofis a square wave which is at a minus voltage when c is positive and atzero volt when c is negative. lf zero volt at the output of amplifier108 is taken to be a binary one, and the minus voltage, such as about 6volts, is taken to be a binary zero, then the output of amplifier 108may be designated as the signal G.

The signal 6 is applied to a logic stage 110 which may be designated aNAND circuit, the latter being the type logic circuit generally used inthe circuit of FIG. 5. In the NAND circuit 110, a zero input theretoprovides a minus volts output (binary zero), and a minus volts inputthereto provides a zero volt output (binary one). The equations for thefunction of a NAND circuit may be written as X=H+b, x a-b and =a-bwherein x is the output and a and b are inputs. Consequently, the signalG at the output of amplifier 108 is inverted in logic circuit 110 toprovide the signal G.

The signal e' is applied to a sensing amplifier 104. Amplifier 104 is acircuit similar to the circuit of stage 108 and which provides a minusvolts output when the input thereto is equal to or greater than zerovolt and a zero volt output when the input thereto is less than zerovolt. In this amplifier, accordingly, only the negative going portion ofsignal e is amplified and inverted to provide a signal convenientlydesignated as M which is the basic firing signal for the positivecontrolled switching device R,,.

The signal e is also applied to a sensing amplifier 106 wherein thenegative portion of the signal e is clipped and only the positivelygoing portion is inverted and amplified to provide the signalconveniently designated as fi The signal if is inverted in a logiccircuit 112 which is a circuit the same as circuit 110, to provide thesignal M which is the basic firing signal for the negative controlledswitching device. Circuit 106 is one wherein a zero volt output (binaryone) is produced when the input thereto is equal to or less than zerovolt and a minus volts output (binary zero) is produced when the inputthereto exceeds zero volt.

The e,. signal is applied to an input sensing amplifier 114 similar tothat of stages 104 and 108 wherein the negative portion of the signal eis clipped and the positive portion is amplified and inverted to providethe signal r. Signal r is inverted in a logic circuit 116 which is thesame as the circuits of the other logic stages, such as stages 110 and112, to provide the signal P.

The signals G, Mn and r are applied to a logic circuit 118 to provide atthe output thereof the signal GM F and the G, M and r signals areapplied to a logic circuit 120 to provide at the output thereof thesignal GM r.

The GM signal is applied through a differentiating circuit comprising aseries connected capacitor 122 and a parallel connected resistor 124 andthence through the cathode to anode path of a diode 126 to provide sharpnegative pulses occurring at the leading edges of the pulses fed intothe differentiating circuit, these sharp pulses being applied to anamplifier 128. The output of amplifier 128 energizes relay R which isthe negative controlled switching device of the back to back pair ofswitching devices to effect the closing of normally open contacts R Thee: signal which is the ri signal provided from the circuit of FIG. 3 andis the negative of a voltage proportional to the current from the egenerator output voltage is applied to a sensing amplifier 130. Suchsignal can be applied to sensing amplifier 130 since the energization ofswitching device R by amplifier 128 has caused normally open contacts Rassociated therewith to close. Sensing amplifier 130 comprises a circuitwhich provides a binary one output (zero volt) when the input thereto isequal to or less than zero volt and a binary zero output (such as 6volts) when its input is greater than zero volt. Accordingly, in sensingamplifier 130, the negative portion of the -e signal is clipped and thepositive portion is amplified and inverted. The output signal of sensingamplifier 130 may be designated as I and is negative whenever currentflows through switching device R This I signal when applied to amplifier128 maintains switching device R in its energized state after thenegative pulse from diode 126 decays. Switching device R becomesdeenergized when the current signal -e dies out. The latterdeenergization occurs before the next negative pulse from diode 126.

The (m signal is differentiated by a series connected capacitor 132 anda parallel connected resistor 134 and the difierentiated signalsresulting therefrom which comprises a train of sharp negative pulsesoccurring at the leading edges respectively of the pulses from theoutput of logic circuit 120 are applied through the cathode to anodepath of a diode 136 to a sensing amplifier 138. Sensing amplifier 138 isa circuit which provides a binary one output (zero volt) when the inputthereto is negative and a binary zero output such as 6 volts when theinput thereto is equal to or more than zero volt.

It is to be understood that in the signal designation, the term Rsignifies the energized state of the switching device R and the term Fsignifies the energized state of switching device R It is seen that thesignal 6H,? is the negative of the expression which is required to firethe positive controlled switching device R (as will be furtherexplained). Thus the R signal is the inversion of W signal. This Rsignal at the output of sensing amplifier 138 is inverted in anamplifier 140 which is a circuit the same as amplifier 128. The R signalwhich is a binary one or zero volt output causes the deenergization ofswitching device R.,. Accordingly, when it is so deenergized, the esignal is applied to sensing amplifier 138 through normally closedcontacts R the positive portion of the e signal is clipped and thenegative portion is amplified and inverted in stage 138. This positivesignal from stage 138 is inverted in amplifier 140 to provide zerooutput therefrom and relay R is held deenergized until the current fromthe -e signal falls to zero.

In FIG. 6 there is shown the arrangement for combining the signals forenergizing devices R and R It is seen from this figure that when the Rsignal is present, the R normally open contacts close and current flowsthrough relay coil R and when the R signal is present, R is deenergizedand the normally closed contacts R remain closed and current also flowsthrough relay R In FIG. 7 there is shown a circuit suitable for use asthe sensing amplifiers stages 104. 108 and 114 of FIG. 5. In thiscircuit, the input is applied to the base 144 of a PNP transistor 142through a resistor 146. Base 144 is connected to a positive pontentialsource 148 through a resistor 150, the emitter 152 is connected toground and the collector 154 is connected to a negative potential source158 through a resistor 156. A plurality of outputs may be taken atcollector 154.

Transistor 142 is biased for operation whereby with an input equal to orgreater than zero volt applied at base 144, the output at collector 154has a minus volts value. suitably about -6.0 volts (a When the input atbase 144 is less than zero volt, the output at collector 154 is aboutzero volt (a l).

In FIG. 8, there is shown a circuit suitable for use as the sensingamplifier of stage 106 in FIG. 5. In this circuit, the input is appliedthrough a resistor 160 to the base 164 of a transistor 162. Base 164 isconnected to a source of negative potential 166 through a resistor 168,and may be connected to a source of positive potential 170 of a chosenvalue through the anode to cathode path of a diode 173 (shown in dashedlines) whereby the potential at base 164 is positively clamped to thepotential from source 170. The emitter 172 is connected to ground andthe collector 174 is connected to a negative potential source 166through a resistor 176. A plurality of outputs may be taken at collector174.

In the operation of the circuit of FIG. 8, transistor 162 is so biasedfor operation whereby an input at base 164 having a value of zero voltor a minus voltage provides an approximately zero volt output atcollector 174 which may be designated as a binary one. A voltage at base164 which exceeds zero volt provides a negative voltage output, suitablyabout -6 volts at collector 174, such output being convenientlydesignated as a binary zero.

In FIG. 9, there is shown a circuit suitable for use as the sensingamplifier of stage 138 of FIG. 5. In this circuit the inputs are appliedto the base of a PNP transistor 178 through resistors 182 and 184respectively, base 180 being connected to a source of positive potential186 through a resistor 188. The emitter 190 is connected to ground andthe collector 192 is connected to a negative potential source 194through a resistor 196.

In this circuit, transistor 178 is so biased for operation whereby uponthe application of a voltage which has a value less than zero volt tobase 180, an approximately zero volt output is produced at collector192, such output being conveniently designated as a binary one. Wherethe voltage applied to base 180 is equal to or greater than zero, thereis produced at collector 192, a voltage which has a minus value,suitably -6 volts and which may be conveniently referred to as a binaryzero. The logic equation for the circuit of FIG. 9 may be described as xa+b wherein x is the binary one output and a and b are separate binaryzero inputs, the b input actually being an analog quantity where b:l(binary) when its voltage is equal to or greater than zero volt and b=0(binary) when it is a negative voltage.

In a circuit of FIG. 10, there is shown a sensing amplifier suitable foruse in stage 130 of FIG. 5. In this circuit, the inputs are appliedthrough resistors 206 and 208 to the base 202 of a transistor 198, base202 being connected to a source of negative potential 210 throughresistor 212. The emitter 200 is connected to ground and the collector204 is connected to source 210 through a resistor 214.

Transistor 198 is so biased for operation whereby when the input to base202 exceeds zero volt, the output at collector 204 is a negative voltagequantity, such as about 6 volts (binary 0). When the input to base 202is equal to or less than zero volt. the output at collector 198 is aboutzero volt, i.e., a binary one. The logic equation for the amplifier ofFIG. 10 may be stated as x=5+a The b voltage input is an analog quantityand may be defined as: b=l (binary) when its value exceeds zero volt andb=0 (binary) when its value is equal to or less than zero volt.

The circuit of FIG. 11 is suitable for use as a circuit in the logicstages of FIG. 5 such as stages 110, 112, etc. Such circuit isconveniently designated as a NAND type which in effect includes an ANDfunction followed by a NOT function or negation. In this circuit, the aand b inputs are applied through resistors 240 and 242 to the base 246of a transistor 244, base 246 being connected to a positive potentialsource 248 through a resistor 250. The collector 252 is connected to anegative potential source 254 through a resistor 256 and the emitter isconnected to ground. The equations for the circuit of FIG. 11 may bestated as output X=H+R x a-ii and i' a'b.

In FIG. 12, there is shown a circuit suitable for use in the amplifierstages 128 and 140 of FIG. 5. In this circuit, the inputs are appliedthrough resistors 224 and 226 to the base 218 of a PNP transistor 216.The emitter 220 is connected to ground and the collector 222 isconnected to a source 228 of negative potential through the switchingdevice being actuated and depicted as a relay coil 230, coil 230 beingshunted by the cathode to anode path of a diode 231 to clamp collector222 at the potential of source 228 and to eliminate inductance surge.The base 218 is connected to a source of positive potential 234 througha resistor 232.

In this circuit, transistor 216 is so biased for operation whereby anegative input to base 218 provides current through coil 230 whereby itis energized. The logic equations in the circuit of FIG. 12 may bewritten as, R=H+h and F=a-b wherein R signifies the energized state ofcoil 230 and i signifies the deenergized state of coil 230. Utilizingthe designation of the signals as shown in connection with amplifier 128in FIG. 5, then the logic equations for the circuit of FIG. 12 becomes R=GM +I R since the input to amplifier 128 is M,,+T,,.

Reference is now made to the circuit of FIG. for an explanation of theoperation thereof. It is recalled that the function of this circuit isto provide a schedule for firing switching devices R and R schematicallydepicted as relay coils but together behaving as a back to back pair ofswitching devices such as silicon controlled rectifiers, thyratrons andthe like.

The contacts designated R in the circuit of FIG. 2 and the two pairs ofcontacts R shown at the input at integrator 62 in the circuit of FIG. 3depict the equivalent of the operation of a back to back switchingdevice pair.

The input signals to the circuit of FIG. 5 as previously explained arereceived from the circuit of FIG. 3. They are e =e =one generatorvoltage phase. The term e' =the resultant of the mixing of the one phaseof the output of oscillator 90 and the cosinusoid of e (in this example,one half voltage e plus 6 and the providing of two thresholds byclipping out the mid-region of the e signal by the neutral zone circuit.The signal c is the negative of the voltage across a switching devicepair where e,- equals e e'. The voltage e; is the negative of a voltageproportional to the current from the output phase e These analog inputsignals are fed into sensing amplifiers which convert them to on-off,i.e., digital signals. The latter digital signals are mixed and fedthrough logic amplifiers until the final result is the operation of theoutput switching device pair (R and R in FIG. 5.

As previously explained above, two digital states are described asbinary one and binary zero. Binary one signifies the presence of asignal and is a state when the circuit voltage is approximately zerovolt. The binary zero state signifies the absence of a signal and existswhen the voltage is approximately a suitable negative voltage such asabout 6 volts.

The conditions for the operation of switching device R which mayrepresent a silicon controlled rectifier having its anode connected tothe e generator voltage, i.e., it may represent the positive controlledrectifier in a back to back pair and for the operation of switchingdevice R, which may represent a silicon controlled rectifier having itscathode connected to the e generator voltage, i.e., it may represent thenegative controlled rectifier of the back to back pair are as follows:

Conditions for effecting conduction in positive controlled device RPositive firing signal is present M (Derived from input e and theswitching device pair voltage is positive r Derived from -e and Thegenerator voltage e (same as e is positive; G or current i is presentand positive I (The I signal can only be true if the contacts Rassociated with the positive controlled rectifier are closed and currentstarts to flow (derived from e,).)

Conditions for effecting conduction in negative controlled device RNegative firing signal is present M (derived from e and Switching devicepair voltage is negative F (i.e., anode of the negative controlledsilicon controlled rectifier woud be positive, derived from -e,); and

The generator voltage c is negative G (The condition for the negativecontrolled rectifier to have positive anode voltage); or Current i ispresent and negative I (The I signal is true only after the contacts Rassociated with the negative controlled rectifier are closed and currentstarts to flow, such current being derived from -e Thus, the followingequations may be written:

Equation 4 stands for the proposition that relay R (FIG. 6) is actuatedwhen signals M and r and G are concurrently present or have been present(to produce R and I is present or the signal M is present andconcurrently the signals r and g are not present, or this combinationhas been in existence (to produce R and the signal I is present.

In connection with Equation 4, it is to be noted that the I and I termsdo not cause the actuation of relay R since the currents responsible forthese terms cannot flow until the relay R is already actuated. Thus,these terms function to hold relay R actuated until the current drops tozero. This is a characteristic inherent in a switching device such as athyratron or a silicon controlled rectifier R of FIG. 3.

In the circuit of FIG. 5, as has been set forth hereinabove, inputvoltage e may vary widely in frequency but in general is many timesgreater than the reference voltage frequency from oscillator andconsequently, equally many times greater than the output frequency ofthe system. The e signal is amplified and inverted by sensing amplifier108. Since the voltage to switch amplifier 108 on and off may be chosento be relatively small, such as about one volt, compared to themagnitude of the e voltage, the output of amplifier 108 is essentially asquare wave and is negative (binary zero) when voltage e is positive andpositive (binary one) when voltage e is negative. This provides thesignal '6 appearing in Equations 2 and 4 above. The e signal is invertedin logic circuit 110 to produce the signal G appearing in the Equations1 and 4.

The input sensing amplifier 106 amplifies and inverts only the positiveportion of the -e' voltage and its output accordingly becomes fin or theinverse (negative). The fin signal is inverted by logic circuit 112 toproduce the Mn signal which is the basic firing angle signal for thenegative controlled switching device.

The signal e is also fed into the sensing amplifier 104 whereby only thenegative going portion of the -e' signal is amplified. The output ofamplifier 104 is the signal M which is the basic firing signal for thepositive controlled switching device.

The signal e,, i.e., the voltage across a back to back pair of switchingdevices is amplified and inverted by sensing amplifier 114 to producethe signal r which is inverted in logic circuit 116 to provide thesignal Y.

The signals E, M and F are fed into logic circuit 118 to produce thesignal GM F. From Equation 2 it is seen that this is negative of a termrequired to actuate the negative controlled switching device.

The differentiating circuit comprising capacitor 122 and resistor 124produces short duration negative going pulses at the leading edges ofthe wider pulses fed into the differentiating circuit. Each of thesenegative going pulses are amplified in amplifier 128 and the outputthereof actuates switching device R representing conduction therein. Thecontacts R associated with switching device R close upon theenergization of device R to permit signal e to be fed into sensingamplifier 130. Since ampli fier 130 is biased for operation whereby itonly amplifies positive signals, the output of amplifier 130 is thesignal I This signal is negative whenever the negative current isflowing and is the correct polarity to hold the switching device Ractuated even after the negative pulse from the differentiating circuitdecays. After the signal e decays, device R becomes deenergized, suchdeenergization occurring prior to the next pulse from the output of thedifferentiating circuit.

The signals G, M and r are fed into logic circuit 120.

Its output is according to Gi l Q1 This term is the negative of theexpression required to fire the positive controlled switching device asshown in Equation 1. The signal GM r is differentiated in thedifferentiating circuit comprising capacitor 132 and resistor 134 withthe pulses resulting therefrom being applied to sensing amplifier 138.In amplifier 138, the pulses are inverted, the output of sensingamplifier 138 being applied to output amplifier 140, the output ofamplifier 140 causing the deenergization of switching device R Thus, theterm R represents the open or deenergized state of device R and term irepresents its actuated state. When switching device R is in thedeenergized state, the normally closed contacts R associated therewithpermit the application of the -e; signal to sensing amplifier 138. Sincethis amplifier only senses the negative portion of the signal --e suchsensing is the correct polarity for the e signal to hold device R in theunactuated state until the current drops to zero. The wave shapes ofsignals at the various points in the circuit of FIG. are shown therein.

In FIGS. 13-16 taken together as in FIG. 17 there is shown a depictionof another embodiment of a system according to the invention whereinsilicon controlled rectifiers are utilized as the switching devices toprovide frequency conversion. These figures show the details of amodulator for providing one of three phase power outputs from thesystem, viz., the phase A output. It is, of course, to be realized thatmodulators similar to those utilized in providing the phase A output areutilized to provide the phase B and phase C outputs.

In FIGS. 13-17, generator 300 provides the outputs em, 8 and e theseoutputs being 120 displaced in phase with respect to each other. Thefield coil 302 for generator 300 is energized by an exciter 304 whichmay suitably be of the static type. The three generator outputs are fedback to a voltage regulator contained in stage 304 for providing voltageregulation of the outputs of the generator.

The primary winding 309 of a transformer 310 is connected between the eand e output lines, the voltage appearing at the upper terminal of acenter-tapped secondary winding 311 being applied to summing point 312through a resistor 314. The windings of transformer 310 are so poledwhereby the waveform appearing at sum mining point 312 is 90 displacedin phase with respect to the e signal, i.e., the e cosinusoid which isutilized to establish the firing schedules for the silicon controlledrectifiers associated with the e output of generator 300.

Also, applied to the summing point 312 through a resistor 316 is thephase A output of a three phase sine wave reference oscillator and phasesplitter 320. Oscillator 320 is chosen to have a range of determinablefrequencies which is the desired output range of frequencies, thehighest frequency of such range being substantially less than the lowestfrequency provided from the output of generator 300. The oscillatoroutput for summing point 312 is taken from the lower terminal of thesecondary winding of transformer 320A.

Also applied to the summing point 312 through a resistor 318 is thephase A system output, such output being applied from an autotransformer322 to provide analog feedback as an input to the modulator. It isunderstood that the signal appearing at summing point 312 is utilized toproduce the gating signal for the positive controlled silicon controlledrectifier 400 associated with the e generator output. By the termpositive controlled is meant that silicon controlled rectifier 400 isgated into conductivity during a positive half cycle of the e generatoroutput.

To provide a similar signal such as that appearing at junction point 312in order to produce a gating signal for the negative controlled siliconcontrolled rectifier 404 associated with the e generator output, thesignal appearing at the lower terminal of secondary winding 311 oftransformer 310 is applied to summing point 330 through a resistor 326.The signal appearing at the polarity dot terminal of the secondarywinding of transformer 320A is applied to point 330 through a resistor324 and the signal appearing at the undotted terminal of autotransformer322 is applied to point 330 through a resistor 328.

It is seen that the signal at summing point 330 is of the oppositepolarity as the signal appearing at summing point 312 because of thepoling of secondary winding 311, the poling of the secondary winding oftransformer 320A and the poling of autotransformer 322.

The signal appearing at junction point 312 is applied to the base 334 ofa transistor 332, transistor 332 having an resistor [336] 33]. The base334 is connected to positive nected to a source of positive potential339 through a resistor [336] 331. The base 334 is connected to positivepotential source 339 through a resistor 340 and is negatively clamped toground through the cathode to anode path of a diode 342. The values ofthe circuit components associated with transistor 332 are such wherebyin the quiescent state, base 334 is positively biased and transistor 332conducts at saturation but when current into base 334 goes slightlynegative, transistor 332 is rendered nonconductive. The output appearingat collector 337 is applied directly to the collector 354 of atransistor 350 as will be further explained hereinbelow.

Applied to the base 345 of a transistor 344 through a resistor 346 isthe voltage appearing at the anode 402 of silicon controlled rectifier400 and also applied to base 345 through a center tapped winding 348 anda resistor 347 is the signal appearing at the cathode 401 of siliconcontrolled rectifier 400. In transistor 344, the collector 349 isconnected to the positive source 339 through a resistor 351, the emitter353 is connected directly to ground and the base 345 is connected toground through the cathode to anode path of a diode 355. diode 355serving to negatively clamp to ground base 345. The output appearing atcollector 349 is applied to base 352 of transistor 350.

It has been stated above that the output of collector 337 of transistor332 is directly applied to collector 354 of transistor 350. Intransistor 350. the emitter 356 is connected to ground and the base isconnected to a negative potential source 358 through a resistor 360.Also applied to base 352 through a resistor 362 is an output of areverse current restraining or inhibit circuit 398, such circuitproviding a positive output when current is still flowing in thenegative controlled rectifiers as will be further explained hereinbelow.

The output at collector 354 is applied through series connectedcapacitor 364 to the base 368 of a transistor 366.

In transistor 366, the emitter 370 is connected to ground, a seriesarrangement of resistors 372 and 374 being connected between ground andnegative source 358. The base 368 is connected to the junction 373 ofresistors 372 and 374 through the series arrangement of a feedbackwinding 376 of a blocking oscillator transformer 378 and a resistor 377.The collector 380 is connected to positive source 339 through theparallel combination of a winding 379 of transformer 378 and the seriesarrangement of a resistor 382 and the anode to cathode path of a diode384. The upper terminal of winding 381 of transformer 378, i.e., thepolarity dot terminal is connected to the gate electrode 403 of siliconcontrolled rectifier 400 through a resistor 386 and the lower terminalof winding 381 is connected to the cathode 401 of silicon controlledrectifier 400.

Considering the operation of that portion of the moduator required toprovide the gating signal for silicon controlled rectifier 400, viz,transistors 332, 344, 350, and 366 and their associated circuitcomponents, the voltage from the reference oscillator applied throughresistor 316 to summing point 312 produces a current at the summingpoint which may suitably be designated as I The cosine timing waveapplied through resistor 314 to summing point 312 produces a currentthereat which may be suitably designated as I The sum of these twocurrents analogous to the voltage 2, of FIG. 5, has a similar phaseexcept that it is of the opposite polarity. The analog feedback signal,which contains both the fundamental output frequency and its harmonicsand the modulator ripple voltage derived from the multiple switching ofthe generator voltages and applied to summing point 312 through resistor318 provides a current, I at summing point 312 in accordance therewith.

Since transistor 332 is arranged to conduct at saturation when its baseis substantially at zero volt or slightly higher (0.5 volt) and to benonconductive at a voltage slightly below zero volt (such as 0.5 volt) anegative signal appearing at summing point 312 renders transistor 332nonconductive whereby the positive poential appearing at collector 337is applied to collector 354 of transistor 350.

In transistor 350, the negative potential applied to base 352 throughresistor 360 provides a negative D.C. threshold. In transistor 344, tobase 345 there are supplied through resistors 346 and 347 respectively,currents in accordance with the signals appearing at the anode 402 andcathode 401 of silicon controlled rectifier 400. The output at collector349 of transistor 344 is negative only when e output of generator 300applied to anode 402 of silicon controlled rectifier 400 is positivewith respect to cathode 401. Since the signal appearing at base 345reflects the difference between the voltages at anode 402 and cathode401 of silicon controlled rectifier 400, in the event that such voltageat anode 402 is positive with respect to the voltage on cathode 401,then transistor 344 is rendered conductive to provide essentially a zerovolt output at collector 349. In the event that the voltage at anode 402is negative with respect to cathode 401, then transistor 344 is renderednonconductive and the output at collector 349 is positive. Accordingly,transistor 344 provides a reverse polarity inhibit feature, sucharrangement permitting the gating pulse for silicon controlled rectifier400 to occur only when the voltage applied to anode 402 is positive. Thesignal produced at collector 349 of transistor 344 is analogous to thesignal 5 produced in the modulator of FIG. 5.

It is seen that in the event the voltage at anode 402 of siliconcontrolled rectifier 400 is not positive whereby transistor 344 isnonconductive and transistor 350 is consequently heavily conductive,collector 354 of transistor 350 short circuits to ground the outputappearing at collector 337 of transistor 332 so that no positive signalscan be produced.

Capacitor 364 is included to provide short duration pulses which areproduced at the beginning of each pulse period of the signal. Transistor366 and windings 376, 379 and 381 provide a blocking oscillator, suchblocking oscillator operation being provided by the feedback winding376. Diode 384 is included for transient suppression so that aninductance surge will not cause the voltage at collector 380 to exceedbreakdown. lt is appreciated that in the [evennt] event that the outputof collector 380 is near zero voltage, then a positive pulse appears atthe polarity clot terminal of winding 381 to gate silicon controlledrectifier 400 into conductivity.

The voltage applied from negative source 358 to base 352 throughresistor 360 maintains transistor 350 in the nonconductive state when nosignal (positive) is present at base 352 of transistor 350. This permitscollector 337 of transistor 332 to go positive when the summing pointvoltage at base 334 goes negative, thus actuating blocking oscillatortransistor 366 to provide output gating pulses. It is realized that thesignal on base 334 of transistor 332 and the signal on base 352 oftransistor 350 must both be negative to allow the two collectors 337 and354 (connected together) to go positive and trigger the blockingoscillator. The bias resistor 360 assures that transistor 350 isnonconductive except when either of the aforesaid inputs is positive(NOR circuit).

In FIG.22a, there is shown the compositive wave shape of the currents atsumming point 312 comprising A.C. bias current (I superimposed on thereference oscillator current (-1 and a feedback current proportional tothe system output voltage.

The restraining circuit output signal when positive also functions torender transistor 350 conductive whereby the blocking oscillator doesnot produce output gating pulses. It will be further explained belowthat a restraining circuit output signal reflects a condition whereincurrent is still flowing in the negative controlled rectifiers wherebycommutation to the positive controlled rectifiers is prevented by suchrestraining circuit output signal.

In FIG. 22b there is shown the signal observed at collector 337 oftransistor 332 when the collector circuitof transistor 350 is opened.FIG. 22c shows the signal appearing at collector 337 of transistor 322when transistor 350 is connected into the circuit. At first glance, itwould appear that the wave shape FIG. 22c should follow the dotted linewith the pulse remaining until the controlled rectifier polarity isreversed. However, as soon as silicon controlled rectifier 400 isswitched into conductivity, the voltage across it abruptly drops down toa very small figure such as about one volt. The design of the circuitcomprising transistor 344 and its associated components is such thatwith so small a voltage appearing at anode 402 of silicon controlledrectifier 400, transistor 344 is not rendered conductive and a reversepolarity inhibit signal is produced which causes the wave shape at theoutput at collector 337 to rapidly drop to zero as soon as siliconcontrolled rectifier 400 is rendered conductive. If for any reasonsilicon controlled rectifier 400 is not rendered conductive when itshould have been, then the wave shape of the output at collector 337follows the dotted line of FIG. 22c.

The waveform of FIG. 22d shows the output of the blocking oscillatorwith its short duration pulse and the waveform of FIG. 22c shows thegenerator signal e (e and e have the same wave shape), the hatchedportions therein indicating when silicon controlled recti fier 400conducts. It is to be noted that the positive controlled siliconcontrolled rectifier is essentially being switched into conductivityduring the negative half cycle from the reference oscillator output.

The portion of the modulator for providing the gating signals forsilicon controlled rectifier 404 which is in back to back relation withsilicon controlled rectifier 400, i.e., it is controlled by the negativehalf cycles of the e output, is the same as that portion for providingthe gating signals for silicon controlled rectifier 400, the polarity ofthe secondary windings of transformers 310, 320A and 322 insuring thatthe same operation occurs therein. From the waveform of FIG. 22a, it isaccordingly seen that a negative controlled silicon controlled rectifieris fired during the positive half cycle of the reference oscillatoroutput.

2. IN COMBINATION WITH A VARYING FREQUENCY POWER SOURCES HAVING A CHOSENPLURALITY OF LIKE BALANCED PHASE OUTPUTS, SAID CHOSEN PLURALITY OFFREQUENCY CONVERSION MEANS, EACH OF SAID CONVERSION MEANS COMPRISINGSAID CHOSEN PLURALITY OF FIRST AND SECOND SILICON CONTROLLED RECTIFIERS,EACH OF SAID SILICON CONTROLLED RECTIFIERS COMPRISING AN ANODE, ACATHODE AND A GATE ELECTRODE, THE ANODE OF EACH OF SAID FIRST SILICONCONTROLLED RECTIFIERS RESPECTIVELY BEING COUPLED AT ONE OF SAID POWERSOURCE OUTPUTS, THE CATHODE OF EACH OF SAID SECOND SILICON CONTROLLEDRECTIFIERS RESPECTIVELY BEING CONNECTED TO ONE OF SAID POWER SOURCEOUTPUTS, A REFERENCE VOLTAGE SOURCE HAVING SAID CHOSEN PLURALITY OFBALANCED PHASE OUTPUTS, THE FREQUENCY OF SAID REFERENCE VOLTAGES BEINGLESS THAN THE LOWEST FREQUENCY OF THE OUTPUTS FROM SAID POWER SOURCE,SAID CHOSEN PLURALITY OF MODULATING MEANS, EACH OF SAID MODULATING MEANSBEING IN CIRCUIT WITH THE OUTPUTS OF SAID POWER SOURCE AND ONE OF THEOUTPUTS OF SAID REFERENCE VOLTAGE SOURCE FOR MIXING SAID POWER SOURCEOUTPUTS WITH SAID REFERENCE VOLTAGE, MEANS FOR APPLYING THE RESPECTIVEOUTPUTS OF SAID MODULATING MEANS TO THE GATE ELECTRODES OF SAID SILICONCOTROLLED RECTIFIERS COMPRISING CORRESPONDING ONES OF SAID FREQUENCYCONVERSION MEANS, SAID CHOSEN PLURALITY OF MEANS FOR RESPECTIVELYCOMBINING THE OUTPUTS OF THE SILICON CONTROLLED RECTIFIERS INCLUDED INEACH OF SAID FREQUENCY CONVERSION MEANS TO PROVIDE SAID CHOSEN PLURALITYOF BALANCED PHASE SYSTEM OUTPUTS, THE CATHODES OF SAID FIRST RECTIFIERSAND THE ANODES OF SAID SECOND RECTIFIERS BEING CONNECTED